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1 amp/1.5 amp/2 amp synchronous, step - down dc - to - dc converters data sheet adp2105/adp2106/adp2107 rev. d information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trad emarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062 - 9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ? 2006 C 2012 analog devices, inc. all rights reserved. features extremely h igh 9 7 % efficiency ultralow quiescent current: 20 a 1.2 mhz switching frequency 0.1 a shutdown supply current maximum load current adp2105: 1 a adp2106: 1.5 a adp2107: 2 a input v oltage : 2.7 v to 5.5 v output v oltage : 0.8 v to v in max imum duty c ycle: 100% smoothly transitions into low dropout (ldo) m ode internal synchronous rectifier small 16 - lead 4 mm 4 mm lfcsp_vq p ackage optimized for small ceramic output capacitors enable/s hutdown logic input undervoltage l ockout soft s tart suppo rted by adisimpower ? design tool applications mobile h andsets pdas and palmtop c omputers telecommunication/ n etworking e quipment set top b oxes audio/v ideo consumer e lectronics general description the adp21 05/ adp210 6/ adp210 7 are low quiescent current , synchronous, step - down dc - to - dc converters in a compact 4 mm 4 mm lfcsp _vq package. at medium to high load currents, these devices use a current mode, constant frequency pulse - width modulation (pwm) control s cheme for excellent stability and transient response. to ensure the longest battery life in portable applications, the adp2105/ adp210 6/ adp210 7 use a pulse frequency modulation (pfm) control scheme under lig ht load conditions that reduces switching frequenc y to save power . the adp2105/ adp210 6/ adp210 7 run from input voltages of 2.7 v to 5.5 v , allowing single li+ /li ? polymer cell, multiple alkaline/nimh cells, pcmcia, and other standard power sources. the output voltage of adp2105/adp2106/adp210 7 is adjustabl e from 0.8 v to the input voltage (indicated by adj ) , wh ereas the adp2105/ adp2106/adp2107 are available in preset output voltage options of 3.3 v, 1.8 v, 1.5 v, and 1.2 v (indicated by x . x v ) . each of these variations is available in three maximum current levels : 1 a (adp2105), 1.5 a (adp2106), and 2 a (adp2107). the power switch and synchronous rectifier are integrated for minimal external part count an d high efficiency. during logic controlled shutdown , the input is disconnected from the output , and it dr aws less than 0.1 a from the input source. o ther key features include under voltage lockout to prevent deep battery discharge and programmable soft start to limit inrush current at startup. typical operating ci rcuit adp2107-adj off en ss lx2 fb pwin1 agnd output voltage = 2.5v comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 2.7v to 5.5v 10f fb 1nf 70k 120pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2h 4.7f load 0a to 2a 10f 10f 10 0.1f nc = no connect 06079-002 85k 40k fb figure 1. circuit configuration of adp2107 with v out = 2.5 v 100 75 0 2000 06079-001 load current (ma) efficiency (%) 95 90 85 80 200 400 600 800 1000 1200 1400 1600 1800 v in = 3.3v v in = 3.6v v in = 5v v out = 2.5v figure 2. efficiency vs. load current for the adp2107 with v out = 2.5 v
adp2105/adp2106/adp2107 data sheet rev. d | page 2 of 36 table of contents features .............................................................................................. 1 applications ....................................................................................... 1 general description ......................................................................... 1 typical operating circuit ................................................................ 1 revision history ............................................................................... 2 functional block diagram .............................................................. 3 specifications ..................................................................................... 4 absolute maximum ratings ............................................................ 6 thermal resistance ...................................................................... 6 boundary condition .................................................................... 6 esd caution .................................................................................. 6 pin configuration and function descriptions ............................. 7 typical perform ance characteristics ............................................. 8 theory of operation ...................................................................... 14 control scheme .......................................................................... 14 pwm mode operation .............................................................. 14 pfm mode operation ................................................................ 14 pulse - skipping threshold ......................................................... 14 100% duty cycle operation (ldo mode) ............................. 14 slope compensation .................................................................. 15 design features ........................................................................... 15 applications information .............................................................. 16 external component selection ................................................ 16 setting the output voltage ........................................................ 16 inductor selection ...................................................................... 17 output capacitor selection ....................................................... 18 input capacitor selection .......................................................... 19 input filter ................................................................................... 19 soft start period .......................................................................... 19 loop compensation .................................................................. 19 bode plots .................................................................................... 20 load transient response .......................................................... 21 efficiency considerations ......................................................... 22 thermal considerations ............................................................ 22 design example .............................................................................. 24 external compone nt recommendations .................................... 25 circuit board layout recommendations ................................... 27 evaluation board ............................................................................ 28 evaluation board schematic for adp2107 (1.8 v) ............... 28 recommended pcb board layout (evaluation board layout) ......................................................................................... 28 a pplication circuits ....................................................................... 30 outline dimensions ....................................................................... 33 ordering guide .......................................................................... 33 revision history 8 /1 2 rev. c t o rev. d change to features section ............................................................. 1 added exposed pad notation to pin configuration and function description section ......................................................... 7 added ad isimpower design tool section ................................. 16 updated outline dimensions ....................................................... 33 9 /0 8 rev. b to rev. c changes to table summary statement .......................................... 4 chang es to lx minimum on - time parameter, table 1 ............. 5 7 /0 8 rev. a to rev. b changes to g eneral d escription section ...................................... 1 changes to figure 3 .......................................................................... 3 changes to table 1 ............................................................................ 4 changes to table 2 ............................................................................ 6 changes to figure 4 .......................................................................... 7 changes to table 4 ............................................................................ 7 changes to figure 26 ...................................................................... 11 changes to fig ure 31 t hrough figure 34 .................................... 12 changes to figure 35 ...................................................................... 13 changes to pmw mode operation section and pulse skipping threshold section ........................................................................... 14 changes to slope compensation section .................................... 15 changes to setting the output voltage section ........................ 16 changes to figure 37 ...................................................................... 16 changes to inductor selection section ........................................ 17 changes to input capacitor selection section ........................... 18 changes to figure 47 t hrough figure 52 ..................................... 21 changes to transition losses section and thermal consideration s section .................................................................. 22 changes to table 11 ....................................................................... 2 5 changes to circuit board layout recomm endations section ..27 changes to table 12 ....................................................................... 2 6 changes to figure 53 ...................................................................... 28 changes to figure 56 t hrough figure 57 .................................... 30 changes to figure 58 t hrough figure 59 .................................... 31 changes to outline dimensions .................................................. 33 3/07 rev. 0 to rev. a updated format .................................................................. universal changes to output chara cteristics and lx (switch node) characteristics sections ................................... 3 changes to typical performance characteristics section ........... 7 changes to load transient response section ............................ 21 7/06 revision 0: initial version
data sheet adp2105/adp2106/adp2107 rev. d | page 3 of 36 functional block dia gram 14 13 9 in pwin1 pwin2 12 10 lx2 11 pgnd lx1 2 gnd 7 agnd 16 fb 16 fb 6 ss 5 comp 3 gnd 4 gnd 8 nc 15 gnd 1 en soft start reference 0.8v gm error am p for preset volt age options on l y pwm/ pfm contro l current limit zero cross comparator thermal shutdown current sense amplifier driver and anti- shoot through slope compens a tion oscill a t or 06079-037 figure 3.
adp2105/adp2106/adp2107 data sheet rev. d | page 4 of 36 specifications v in = 3.6 v @ t a = 25c, unless otherwise noted. 1 table 1 . parameter min typ max unit conditions input characteristics input voltage range 2.7 5.5 v ?40c t j +125c undervoltage lockout threshold 2.4 v v in rising 2.2 2.6 v v in rising , ?40c t j +125c 2.2 v v in falling 2.0 2.5 v v in falling , ?40c t j +125c undervoltage lockout hysteresis 2 200 mv v in falling output character istics out put regulation voltage 3.267 3.3 3.333 v 3.3 v , load = 10 ma 3.3 v 3.3 v , v in = 3.6 v to 5.5 v, no load to full load 3.201 3.399 v 3.3 v , v in = 3.6 v to 5.5 v, no load to full load , ?40c t j +125c 1.782 1.8 1.818 v 1.8 v , load = 10 ma 1.8 v 1.8 v , v in = 2.7 v to 5.5 v, no load to full load 1.746 1.854 v 1.8 v , v in = 2.7 v to 5.5 v, no load to full load , ?40c t j +125c 1.485 1.5 1.515 v 1.5, load = 10 ma 1.5 v adp210x - 1.5 v , v in = 2.7 v to 5.5 v, no load to ful l load 1.455 1.545 v adp210x - 1.5 v , v in = 2.7 v to 5.5 v, no load to full load , ?40c t j +125c 1.188 1.2 1.212 v 1.2 v , load = 10 ma 1.2 v 1.2 v , v in = 2.7 v to 5.5 v, no load to full load 1.164 1.236 v 1.2 v , v in = 2.7 v to 5.5 v, no load to full load , ?40c t j +125c load regulation 0.4 %/a adp2105 0.5 %/a adp2106 0.6 %/a adp2107 line regulation 3 0.1 0.33 %/v adp2105, measured in servo loop 0.1 0.3 %/v adp2106 and adp2107, measured in servo loop output voltage range 0 .8 v in v adj feedback characteristics fb regulation voltage 0.8 v adj 0.784 0.816 v adj , ?40c t j +125c fb bias current ?0.1 +0.1 a adj , ?40c t j +125c 3 a 1.2 v output voltage 6 a 1.2 v output voltage, ?40c t j +125 c 4 a 1.5 v output voltage 8 a 1.5 v output voltage, ?40c t j +125c 5 a 1.8 v output voltage 10 a 1.8 v output voltage , ?40c t j +125c 10 a 3.3 v output voltage 20 a 3.3 v output voltage , ?40c t j +125c
data sheet adp2105/adp2106/adp2107 rev. d | page 5 of 36 parameter min typ max unit conditions input current characteristics in operating current 20 a adp210x( adj ) , v fb = 0.9 v 30 a adp210x( adj ) , v fb = 0.9 v , ?40c t j +125c 20 a adp210x(x . x v ) output voltage 10% above regulation voltage 30 a adp210x(x . x v ) output voltage 10% above regulation voltage , ?40c t j +125c in shutdown current 4 0.1 1 a v en = 0 v lx (switch ) node characteristics lx on resistance 4 190 m ? p - channel switch , adp2105 270 m ? p - channel switch , adp2105 , ?40c t j +125c 100 m ? p - channel switch , adp2106 and adp2107 165 m ? p - channel switch , adp2106 and adp2107 , ?40c t j +125c 160 m ? n - channel synchronous rectifier, adp2105 230 m ? n - channel synchronous rectifier, adp2105 , ?40 c t j +125c 90 m ? n - channel synchronous rectifier , adp2106 and adp2107 140 m ? n - channel synchronous rectifier , adp2106 and adp2107 , ?40c t j +125c lx leakage curren t 4 , 5 0.1 1 a v in = 5.5 v, v lx = 0 v, 5.5 v lx peak current limit 5 2.9 a p - channel switch, adp2107 2.6 3.3 a p - channel switch, adp2107 , ?40c t j +125c 2.25 a p - channel switch, adp2106 2.0 2.6 a p - channel switch, adp2106 , ?40c t j +125c 1.5 a p - channel switch, adp2105 1.3 1.8 a p - channel switch, adp2105 , ?40c t j +125c lx minimum on - time 1 10 ns in pwm mode of operation, ?40c t j +125c enable characteristics en input high voltage 2 v v in = 2.7 v to 5.5 v , ?40c t j +125c en input low voltage 0.4 v v in = 2.7 v to 5.5 v , ?40c t j +125c en input leakage current ? 0.1 a v in = 5.5 v, v en = 0 v, 5.5 v ?1 +1 a v in = 5.5 v, v en = 0 v, 5.5 v , ?40c t j +125c oscillator frequency 1.2 mhz v in = 2.7 v to 5.5 v 1 1.4 mhz v in = 2.7 v to 5.5 v , ?40c t j +125c soft start period 750 1000 1200 s c ss = 1 nf thermal characteristics thermal shutdown threshold 140 c thermal shutdown hysteresis 40 c compe nsator transconductance ( g m ) 50 a/v current sense amplifier gain (g cs ) 2 1.875 a/v adp2105 2.8125 a/v adp2106 3.625 a/v adp2107 1 all limits at temperature extremes are guaranteed via correlation using standard statistical quality control (sqc). typical v alues are at t a = 25c. 2 guaranteed by design. 3 the adp2105/adp2106/adp2107 line reg ulation was measured in a servo loop on the automated test equipment that adjusts the feedback voltage to achieve a specific comp voltage. 4 all lx (switch) node characteristics are guaranteed only when the lx1 pin and lx2 pin are tied together. 5 these sp ec ifications are guaranteed from ?40c to +85c.
adp2105/adp2106/adp2107 data sheet rev. d | page 6 of 36 absolute maximum rat ings table 2 . p arameter rating in, en, ss, comp, fb to agnd ?0.3 v to +6 v lx1, lx2 to pgnd ?0.3 v to (v in + 0.3 v) pwin1, pwin2 to pgnd ?0.3 v to +6 v pgnd to agnd ?0.3 v to +0.3 v gnd to agnd ?0.3 v to +0.3 v pwin1, pwin2 to in ?0.3 v to +0.3 v operating junction temperature range ?40c to +125c storage t emperature range ?65c to +150c soldering conditions jedec j - std -020 stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any ot her conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. thermal resistance ja is specified for the worst - case conditions, that is, a device soldered in a circuit board for surface - mount packages. table 3 . thermal resistance package type ja unit 16- lead lfcsp_vq/qfn 40 c/w maximum power dissipation 1 w boundary condition natural conve ction, 4 - layer board, exposed pad soldered to the pcb. esd caution
data sheet adp2105/adp2106/adp2107 rev. d | page 7 of 36 pin configuration an d function descripti ons 06079-003 pin 1 indicator 11 pgnd 12 lx2 10 lx1 9 pwin2 comp 5 ss 6 agnd 7 nc 8 adp2105/ adp2106/ adp2107 top view (not to scale) 15 gnd 16 fb 14 in 13 pwin1 en 1 gnd 2 gnd 3 gnd 4 notes 1. nc = no connect. do not connect to this pin. 2. the exposed pad should be soldered to an external ground plane underneath the ic for thermal dissipation. figure 4 . pin configuration table 4 . pin function descriptions pin no. mnemonic descr iption 1 en enable input. drive en hi gh to turn on the device . drive en low to turn off the device and reduce the input current to 0.1 a. 2, 3, 4, 15 gnd test pins. these pins are used for internal testing and are not ground return pins. t hese pins are to be tied to the agnd plane as close as possible to the adp2105/adp2106/adp2107. 5 comp feedback loop compensation n ode. comp is the output of the internal transconductance error amplifier. place a series rc network from comp to a gnd to compensate the co nverter . see the loop compensation section. 6 ss soft start input. place a capacitor from ss to a gnd to set the soft start period. a 1 nf capacitor sets a 1 ms soft start period. 7 agnd analog ground. connect the ground of the c ompensation components, the soft start capacitor , and the voltage divider on the fb pin to the agnd pin as close as possible to the adp2105/ adp2106/adp2107 . the agnd is a lso to be connect ed to the exposed pad of adp2105/adp2106/adp2107 . 8 n c no connect. this is not internally connected and c an be connected to other pins or left unconnected. 9, 13 pwin 2, pwin1 power source input s . the source of the pfet high - side switch. bypass each pwin pin to the nearest pgnd plane with a 4.7 f or greater capacitor as close as possible to the adp2105/adp2106/ adp2107. see the inpu t capacitor selection section. 10, 12 lx 1, lx2 switch ou tputs. t he drain of the p - channel power switch and n - channel synchronous rectifier. these pins are to be t ie d together and c onnect ed to the output lc filter between lx and the output voltage. 11 pgnd power ground. co nnect the ground return of all input and output c apacitors to the pgnd pin using a power g round plane as close as possible to the adp2105/adp2106/adp 2107 . the pgnd is then to be c onnect ed to the exposed pad of the adp2105/adp2106/adp2107 . 14 in power input. t he power source for the adp2105/adp2106/ adp2107 internal circuitry. connect in and pwin1 with a 10 ? resistor as close as possible to the adp2105 /adp2106/adp2107 . bypass in to a gnd with a 0.1 f or greater capacitor. see the input filter section. 16 fb output voltage sense or feedback input. for fixed output versions, connect to the output voltage. for adjustable versions , fb is the input to the error amplifier. drive fb through a resistive voltage divi der to set the output voltage. the fb regulation voltage is 0.8 v. ep exposed pad. the exposed pad should be soldered to an external ground plane underneath the ic for the rmal dissipatio n.
adp2105/adp2106/adp2107 data sheet rev. d | page 8 of 36 typical performance characteristics 100 1 1000 06079-084 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 60 v in = 5.5v v in = 4.2v v in = 3.6v v in = 2.7v inductor: sd14, 2.5h dcr: 60m? t a = 25c figure 5 . efficiency adp2105 (1.2 v output) 100 1 1000 06079-085 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 60 v in = 3.6v v in = 4.2v v in = 5.5v inductor: cdrh5d18, 4.1h dcr: 43m t a = 25c figure 6 . efficiency adp2105 (3.3 v output) 100 50 1 10k 06079-062 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 2.7v v in = 3.6v v in = 4.2v v in = 5.5v inductor: d62lcb, 2h dcr: 28m? t a = 25c figure 7 . efficiency ad p2106 (1.8 v output) 100 1 1000 06079-086 load current (ma) efficiency (%) 10 100 95 90 85 80 75 70 65 v in = 4.2v inductor: sd3814, 3.3h dcr: 93m? t a = 25c v in = 2.7v v in = 3.6v v in = 5.5v figure 8 . efficiency adp2105 (1.8 v output) 100 50 1 10k 06079-008 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 5.5v v in = 4.2v v in = 3.6v v in = 2.7v inductor: d62lcb, 2h dcr: 28m? t a = 25c figure 9 . efficiency adp2106 (1.2 v output) 100 50 1 10k 06079-053 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 4.2v v in = 5.5v v in = 3.6v inductor: d62lcb, 3.3h dcr: 47m? t a = 25c figure 10 . efficiency adp2106 (3.3 v output)
data sheet adp2105/adp2106/adp2107 rev. d | page 9 of 36 100 50 1 10k 06079-010 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 4.2v v in = 5.5v v in = 3.6v v in = 2.7v inductor: sd12, 1.2h dcr: 37m? t a = 25c figure 11 . efficiency adp2107 (1.2 v) 100 50 1 10k 06079-054 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 4.2v v in = 5.5v v in = 3.6v inductor: cdrh5d28, 2.5h dcr: 13m? t a = 25c figure 12 . efficiency adp2107 (3.3 v) 1.85 1.75 0.1 10k 06079-064 load current (ma) output voltage (v) 5.5v, ?40c 5.5v, +25c 2.7v, ?40c 2.7v, +25c 2.7v, +125c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c 1.83 1.81 1.79 1.77 1 10 100 1k figure 13 . output voltage accuracy adp2107 (1.8 v) 100 50 1 10k 06079-063 load current (ma) efficiency (%) 95 90 85 80 75 70 65 60 55 10 100 1k v in = 2.7v v in = 3.6v v in = 4.2v v in = 5.5v inductor: d62lcb, 1.5h dcr: 21m? t a = 25c figure 14 . efficiency adp210 7 (1.8 v) 1.23 1.17 0.01 10k 06079-082 load current (ma) output voltage (v) 5.5v, ?40c 5.5v, +25c 2.7v, ?40c 2.7v, +25c 2.7v, +125c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c 0.1 1 10 100 1k 1.22 1.21 1.20 1.19 1.18 figure 15 . output voltage accuracy adp2107 (1.2 v) 3.38 3.22 0.01 10k 06079-081 load current (ma) output voltage (v) 0.1 1 10 100 1k 3.36 3.34 3.32 3.30 3.28 3.26 3.24 5.5v, ?40c 5.5v, +25c 3.6v, ?40c 3.6v, +25c 3.6v, +125c 5.5v, +125c figure 16 . output voltage accuracy adp2107 (3.3 v)
adp2105/adp2106/adp2107 data sheet rev. d | page 10 of 36 10k 1 0.8 06079-016 input voltage (v) quiescent current (a) 10 100 1k 1.2 1.6 2.0 2.4 2.8 3.2 3.6 4.0 4.4 4.8 5.2 ?40c +125c +25c figure 17 . quiescent current vs. input voltage ?40 125 06079-017 temperature (c) feedback voltage (v) ?20 0 20 40 60 80 100 120 0.795 0.796 0.797 0.798 0.799 0.800 0.801 0.802 figure 18 . feedback voltage vs. temperature 1.75 1.25 06079-073 2.7 5.7 input voltage (v) peak current limit (a) 1.70 1.65 1.60 1.55 1.50 1.45 1.40 1.35 1.30 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 adp2105 (1a) t a = 25c figure 19 . peak current limit of adp2105 190 180 170 160 150 140 130 120 110 100 switch on resistance (m?) 2.7 3.0 3.3 3.6 3.9 4.2 4.5 5.1 5.4 4.8 input voltage (v) pmos power switch nmos synchronous rectifier 06079-093 figure 20 . switch on resistance vs. input voltage adp2105 120 0 2.7 5.4 06079-018 input voltage (v) switch on resistance (m?) 100 80 60 40 20 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 nmos synchronous rectifier pmos power switch t a = 25c figure 21 . switch on resistance vs. input voltage adp2106 and adp2107 1260 1 190 2.7 5.4 06079-021 input voltage (v) switching frequency (khz) 1250 1240 1230 1220 1210 1200 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 ?40c +25c +125c figure 22 . switching frequency vs. input voltage
data sheet adp2105/adp2106/adp2107 rev. d | page 11 of 36 2.35 1.85 06079-072 2.7 5.7 input voltage (v) peak current limit (a) 2.30 2.25 2.20 2.15 2.10 2.05 2.00 1.95 1.90 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 adp2106 (1.5a) t a = 25c figure 23 . peak current limit of adp2106 3.00 2.50 06079-071 2.7 5.7 input voltage (v) peak current limit (a) 2.95 2.90 2.85 2.80 2.75 2.70 2.65 2.60 2.55 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 adp2107 (2a) t a = 25c figure 24 . peak current limit of adp2107 150 0 06079-067 2.7 5.7 input voltage (v) pulse-skipping threshold current (ma) 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 135 120 105 90 75 60 45 30 15 v out = 2.5v v out = 1.2v v out = 1.8v t a = 25c figure 25 . pulse - skipping threshold vs. input voltage for adp2106 06079-074 4 3 1 lx (switch) node output voltage inductor current : 260mv @: 3.26v ch1 1v 45.8% ch4 1a? ch3 5v m 10s a ch1 1.78v t figure 26 . short - circuit response at output 135 0 2.7 5.7 06079-066 input voltage (v) pulse-skipping threshold current (ma) 120 105 90 75 60 45 30 15 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 v out = 1.8v v out = 1.2v v out = 2.5v t a = 25c figure 27 . pulse - skipping thresho ld vs. input voltage for adp2105 195 0 06079-068 2.7 5.7 input voltage (v) pulse-skipping threshold current (ma) 3.0 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 180 165 150 135 120 105 90 75 60 45 30 15 v out = 2.5v v out = 1.8v v out = 1.2v t a = 25c figure 28 . pulse - skipping threshold vs. input voltage for adp2107
adp2105/adp2106/adp2107 data sheet rev. d | page 12 of 36 190 180 170 160 150 140 130 120 110 100 switch on resistance (m?) 2.7 3.0 3.3 3.6 3.9 4.2 4.5 5.1 5.4 4.8 input voltage (v) pmos power switch nmos synchronous rectifier 06079-093 figure 29 . switch on resistance vs. temperature adp2105 ?40 06079-083 junction temperature (c) switch on resistance (m?) ?20 0 20 40 60 80 100 120 0 20 40 60 80 100 120 140 pmos power switch nmos synchronous rectifier figure 30 . swi tch on resistance vs. temperature adp2106 and adp2107 06079-030 ch1 50mv 6% ch4 200ma? ch3 2v m 2s a ch3 3.88v t 3 4 1 inductor current output voltage (ac-coupled) lx (switch) node figure 31 . pfm mode of operation at very light load (10 ma) 06079-033 ch1 50mv 17.4% ch4 200ma? ch3 2v m 400ns a ch3 3.88v t 3 4 1 lx (switch) node output voltage (ac-coupled) inductor current figure 32 . dcm mode of operation at light load (100 ma) 06079-034 ch1 20mv 13.4% ch4 1a? ch3 2v m 2s a ch3 1.84v t 3 4 1 lx (switch) node output voltage (ac-coupled) inductor current figure 33 . minimum off time control at dropout 06079-031 ch1 20mv 17.4% ch4 1a? ch3 2v m 1s a ch3 3.88v t 3 4 1 output voltage (ac-coupled) inductor current lx (switch) node figure 34 . pwm mode of operation at medium/heavy load (1.5 a)
data sheet adp2105/adp2106/adp2107 rev. d | page 13 of 36 06079-032 ch1 1v 45% ch4 1a? ch3 5v m 4s a ch3 1.8v t 3 4 1 induc t or current output vo lt age channel 3 frequency = 336.6khz : 2.86a @: 2.86a lx (switch) node figure 35 . current limit behavior of adp2107 (frequency foldback) 06079-035 ch1 1v 20.2% ch4 500ma? ch3 5v m 400s a ch1 1.84v t 3 4 1 enable voltage inductor current output voltage figure 36 . startup and shutdown waveform (c ss = 1 nf ss time = 1 ms)
adp2105/adp2106/adp2107 data sheet rev. d | page 14 of 36 theory of operation the adp2105/adp2106/adp2107 are step - down, dc - to - dc converters that use a fixed frequency, peak current mode archi - tecture with an integrated high - side s witch and low - side synchron - ous rectifier. the high 1.2 mhz switching frequency and tiny 16- lead , 4 mm 4 mm lfcsp_vq package allow for a small step - down dc - to - dc converter solution. the integrated high - side switch (p - channel mosfet) and synchronous recti fier (n - channel mosfet) yield high efficiency at medium to heavy loads. light load efficiency is improved by smoothly transitioning to variable frequency pfm mode. the adp2105/adp2106/adp2107 ( adj ) operate with an input voltage from 2.7 v to 5.5 v and regu late a n output voltage down to 0.8 v. the adp2105/adp2106/adp2107 are also available with pre set output voltage options of 3.3 v , 1.8 v , 1.5 v, a n d 1.2 v. control scheme the adp2105/adp2106/adp2107 operate with a fixed frequency , peak current mode pwm cont rol architecture at medium to high loads for high efficiency , but shift to a variable frequency pfm control scheme at light loads for lower quies cent c urrent. when operating in fixed frequency pwm mode, the duty cycle of the integrated switches is adjuste d to regulate the output voltage, but when operating in pfm mode at light loads, the switching frequency is adjusted to regulate the output voltage. the adp2105/ adp210 6/ adp210 7 operate in the pwm mode only when the load cu rrent is greater than the pulse - s kipping threshold current. at load currents below this value, the converter smoothly transitions to the pfm mode of operation. pwm mode operation in pwm mode, the adp2105/ adp210 6/ adp210 7 operate at a fixed frequency of 1.2 mhz set by an internal oscillator . at the start of each oscillator cycle, the p - channel mosfet switch is turned on, putting a positive voltage across the inductor. current in the inductor increases until the current sense signal crosses the peak inductor cu rrent level that turns off the p - c hannel mosfet switch and turns on the n - channel mosfet synchro - nous rectifier. this puts a negative voltage across the inductor, causing the inductor current to decrease. the synchronous rectifier stays on for the r emainder of the cycle , unless t he induc tor current reaches zero, which causes the zero - crossing comparator to turn off the n - channel mosfet. the peak inductor current is set by the voltage on the comp pin. t he comp pin is the output of a transconductance error amplifier that compares the feedba ck voltage with an internal 0.8 v reference. pfm mode operation the adp2105/ adp210 6/ adp210 7 smoo thly transition to the variable frequency pfm mode of operation when the load current decreases below the pulse skipping threshold current, switching only as n ecessary to maintain the output voltage within regulation. when the output voltage dips below regulation, the adp2105/ adp2106/adp2107 enter pwm mode for a few oscillator cycles to increase the output voltage back to regulation. during the wait time betwee n bursts, both power switches are off, and the output capacitor supplies all the load current. because the output voltage dips and recovers occasionally, the output voltage ripple in this mode is larger than the ripple in the pwm mode of operation. pulse - s kipping threshold the output current at which the adp2105/ adp210 6/ adp210 7 transition from variable frequency pfm control to fixed frequency pwm control is called the pulse - skipping threshold. the pulse - skipping threshold is optimized for excellent efficien cy over all load currents . the variation of pulse - skipping threshold with input voltage and output voltage is shown in figure 25 , figure 27, and figure 28. 100% duty cycle oper ation (ldo mode) as the input voltage drops , approaching the output voltage, the adp2105/ adp210 6/ adp210 7 smoothly transition to 10 0% duty cycle, maintaining the p - channel mosfet switch - on conti - nuously . this allows the adp2105 /adp2106/adp2107 to regulate the output voltage until the drop in input voltage forces the p - channel mosfet switch to enter dropout, as shown in the following equation: v in(min) = i out ( r ds(on) ? p + dcr ind ) + v out(nom) the adp2105/ adp210 6/ adp210 7 achieve 100% duty cyc le operation by stretching the p - channel mosfet switch - on time if the inductor current does not reach the peak inductor current level by the end of the clock cycle. when this happens, the oscil - lator remains off until the inductor current reaches the peak inductor current level, at which time the switch is turned off and the synchronous rectifier is turned on for a fixed off time. at the end of the fixed off time, another cycl e is initiated. as the adp2105/ adp210 6/ adp210 7 approach dropout, the switching frequency decreases gradually to smoothly transition to 100% duty cycle operation.
data sheet adp2105/adp2106/adp2107 rev. d | page 15 of 36 slope compensation slope compensation stabilizes the internal current control loop of the adp 2105/ adp210 6/ adp210 7 when operating beyond 50% duty cycle to prevent sub harmonic oscillations. it is imple - mented by summing a fixed , scaled voltage ramp to the current sense signal during the on - time of the p - channel mosfet switch. the slope compensation ramp value determines the minimum inductor that can be used to prevent sub harmonic oscillations at a given output voltage. for slope compensation ramp values , see table 5 . for more information see the inductor selection section. table 5 . slope compensation ramp values part slope compensation ramp values adp2105 0.72 a/ s adp2106 1.07 a/ s adp2107 1.38 a/ s design features enable/shutdown drive en high to turn on the adp2105/ adp2 106/ adp210 7. drive en low to turn off the adp2105/ adp210 6/ adp210 7, reducing the input current below 0.1 a. to force the adp2105/ adp210 6/ adp210 7 to automatically start when input power is applied, connect en to in. when shut down, the adp2105/ adp2106/adp21 07 discharge the soft start capacitor , causing a new soft start cycle every time they are re - enabled. synchronous rectification in addition to the p - channel mosfet switch, the adp2105/ adp210 6/ adp210 7 include an integrated n - channel mosfet synchronous rect ifier. the synchronous recti fier improves effi - ciency, especially at low output voltage, and reduces cost and board space by eliminating the need for an external rectifier . current limit the adp2105/adp2106/adp2107 have protection circuitry to limit the di rection and amount of current flowing through the power switch and synchronous rectifier. the positive current limit on the power switch limits the amount of current that can flow from the input to the output, and the negative current limit on the synchron ous rectifier prevents the inductor current from reversing direction and flowing out of the load. short - circuit protection the adp2105/ adp210 6/ adp210 7 include frequency foldbac k to prevent output current run away on a hard short. when the voltage at the fe edback pin falls below 0.3 v, indicating the possi - bility of a hard short at the output, the switching frequency is reduced to 1/4 of the internal oscillator frequency. the reduction in the switching frequency results in more time for the inductor to d isch arge, preventing a runaway of output current. undervoltage l ockout (uvlo) to protect against deep batte ry discharge, uvlo circuitry is integrated on the adp2105/ adp210 6/ adp210 7. if the i nput voltage drops below the 2.2 v uvlo threshold, the adp2105/ adp210 6/ adp210 7 shut down , and both the power switch and synchronous rectifier turn off. when the voltage again rises above the uvlo threshold, the soft start period is initiated , and the part is enabled. thermal protection in the event that the adp2105/ adp210 6/ adp210 7 junction temperatures rise above 140 c, the thermal shutdown circuit turns off the con verter. e xtreme junction temperatures can be the result of high current operation, poor circuit board design, and/o r high ambient temperature . a 40 c hysteresis i s included so that when thermal shutdown occurs, the adp2105/adp2106/ adp2107 do not return to operation until the on - chip tempera - ture drops below 100 c. when coming out of thermal shutdown, soft start is initiated. soft start the adp2105/ adp210 6/ adp210 7 include soft start circuitry to limit the output voltage rise time to reduce inrush curr ent at startup. to set the soft start period, connect the soft start capacitor (c ss ) from ss to a gnd. when the adp2105/adp2106/ adp210 7 are disabled, or if the input vol tage is below the undervoltage lockout threshold, c ss is internally discharged. when the adp2105/adp2106/adp2107 are enabled, c ss is charged through an internal 0.8 a current source, causing the voltage at ss to rise linearly. the output voltage rises lin early with the voltage at ss.
adp2105/adp2106/adp2107 data sheet rev. d | page 16 of 36 applications informa tion adi sim p ower design tool the adp2105/ adp210 6/ adp2107 is supported by adisimpower design tool set. adisimpower is a collection of tools that produce complete power designs optimized for a specific design goal. the tools enable the user to generate a full schematic, bill of materials, and calculate performance in minutes. adisimpower can optimize designs for cost, area, efficiency, and parts count while taking into consideration the operating conditions and limitations of the ic and all real external components. for more information about adisimpower design tools, refer to www.analog.com/ adisimpower . the tool set is available from this website, and users can also request an unpopulated board throu gh the tool. external component s election the e xternal component selection for the adp2105/ adp210 6/ adp210 7 application circuit s shown in figure 37 and figure 38 depend on input voltage, output voltage , and load current requirements. additionally, trade - offs between performance parameters like efficiency and transient response can be made by varying the choice of external components. setting the output v oltage the output voltage of adp2105/ adp210 6/ adp210 7( adj ) is externally set by a resistive voltage divider from the output voltage to fb. t he ratio of the resistive voltage divider sets the output voltage , and the absolute value of those resistors se ts the divider string current. for lower divider string c urrents, the small 1 0 na (0.1 a maximum) fb bias current is to be taken into account whe n calculating resistor values. the fb bias current can be ignored for a higher divider string current , but this degrades efficiency at very light loads. to l im it outpu t voltage accuracy degradation due to fb bias current to less than 0. 0 5% (0.5% maximum) , ensure that the divider string current is greater than 20 a. to calculate the desired resistor values, first determine the value of the bottom divider string resistor ( r bot ) using the following equation: string fb bot i v r = w here : v fb = 0.8 v, the internal reference. i string is the resistor divider string current. off en ss lx2 agnd output voltage = 1.2v, 1.5v, 1.8v, 3.3v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 5.5v v out c ss r comp c comp 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 l c out load c in2 c in1 10 0.1f nc = no connect adp2105/ adp2106/ adp2107 06079-065 v out fb pwin1 in gnd figure 37 . typical applications circuit for fixed output voltage o ptions of adp2105/adp2106/adp2107 (x . x v )
data sheet adp2105/adp2106/adp2107 rev. d | page 17 of 36 off en ss lx2 fb pwin1 agnd output voltage = 0.8v to v in comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 2.7v to 5.5v fb c ss r comp c comp 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 l c out load c in2 c in1 10 0.1f r top r bot fb nc = no connect adp2105/ adp2106/ adp2107 06079-038 figure 38 . typical applications circuit for adjustable output voltage o ption of adp2105/adp2106/adp2107 ( adj) when r bot is determined, calculate the value of the top resistor ( r top ) by using the following equation: ? ? ? ? ? ? ? = fb fb out bot top v v v r r the adp2105/ adp210 6/ adp2107( x .x v ) include the resistive voltage divider internally, reducing the external circuitry required . for improved load regulation, c onnect the fb to the output voltage as close as possib le to the load. inductor selection the high switching frequency of adp2105/ adp210 6/ adp210 7 allows for minimal output voltage ripple even with small inductors. the si zing of the inductor is a trade - off between efficiency and transient response. a small indu ctor leads to larger inductor current ripple that provides excell ent transient response but degrad es efficiency . due to the high switching frequenc y of adp2105/adp2106/adp2107, shielded ferrite core inductors are recommended for their low core losses and l ow electromagnetic interference (emi) . as a guideline, the inductor peak - to - peak current ripple ( i l ) is typically set to 1/3 of the maximum load current for optimal tr ansient response and efficiency, as shown in the following equations: 3 ) ( ) ( max load sw in out in out l i l f v v v v i ? = ? h ) ( 5 . 2 ) ( max load in out in out ideal i v v v v l ? = ? where f sw is the switching frequency (1.2 mhz). the adp2105/ adp210 6 / adp210 7 use slope compensation in the current control loop to prevent subharmonic oscillations when operating beyond 50% duty cycle. the fixed slope compen - sation limits the minimum inductor value as a function of output voltage. for the adp2105 l > (1.1 2 h/v) v out for the adp2106 l > ( 0.83 h/v ) v out for the adp2107 l > ( 0.66 h/v ) v out inductors 4.7 h or larger are not recommended because they may cause instability in discontinuous conduction mode under light load conditions. i t is also importan t that the induc tor be capable of handling the maximum peak inductor current ( i pk ) determined by the following equation: ? ? ? ? ? ? ? + = 2 ) ( l max load pk i i i table 6 . minimum inductor value for c ommon output voltage options for the adp2105 (1 a) v out v in 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 1.67 h 2.00 h 2.14 h 2.35 h 1.5 v 1.68 h 2.19 h 2.41 h 2.73 h 1.8 v 2.02 h 2.25 h 2.57 h 3.03 h 2.5 v 2.80 h 2.80 h 2.80 h 3.41 h 3.3 v 3.70 h 3.70 h 3.70 h 3.70 h table 7 . minimum inductor value for common output voltage options for the adp2106 (1.5 a) v out v in 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 1.11 h 2.33 h 2.43 h 1.56 h 1.5 v 1.25 h 1.46 h 1.61 h 1.82 h 1.8 v 1.49 h 1.50 h 1.71 h 2.02 h 2.5 v 2.08 h 2.08 h 2.08 h 2.27 h 3.3 v 2.74 h 2.74 h 2.74 h 2.74 h
adp2105/adp2106/adp2107 data sheet rev. d | page 18 of 36 table 8 . minimum inductor value for common output voltage options for the adp2107 (2 a) v out v in 2.7 v 3.6 v 4.2 v 5.5 v 1.2 v 0.83 h 1.00 h 1.07 h 1.17 h 1.5 v 0.99 h 1.09 h 1.21 h 1.36 h 1.8 v 1.19 h 1.19 h 1.29 h 1.51 h 2.5 v 1.65 h 1.65 h 1.65 h 1.70 h 3.3 v 2.18 h 2.18 h 2.18 h 2.18 h table 9 . inductor recommendations for the adp2105/ adp2106/adp2107 vendor small - sized inductors ( < 5 mm 5 mm) lar ge - sized inductors ( > 5 mm 5 mm) sumid a cdrh2d14, 3d16, 3d28 cdrh4d18, 4d22, 4d28, 5d1 8, 6d12 toko 1069as - db3018, 1098as - de2812, 1070as - db3020 d52lc, d518lc, d62lcb coilcraft lps3015, lps4012, do3314 do1605t c ooper bussmann sd3110, sd3112, sd3114, sd3118, sd3812, sd3814 sd10, sd12, sd14, sd52 output capacitor sel ection the output capacitor selection affects both the output voltage ripple and the loop dynamics of the converter. for a given loop crossover freque ncy (the frequency at which the loop gain drops to 0 db) , the maximum voltage transient excursion (overshoot) is inversely proportional to the value of the output capacitor. therefore, larger output capacitors result in improved load transient response. to minimize the effects of the dc - to - dc converter switching, the cross - over frequency of the compensation loop should be less than 1/10 of the switching frequency. higher crossover frequency leads to faster settling time for a load transient response, but it can also cause ringing due to poor phase margin. lower crossover frequency helps to provide stable operation but needs large output capacitors to achieve competitive overshoot specifications. therefore, the optimal crossover frequency for the control loop of adp2105/adp2106/adp2107 is 80 khz, 1/15 of the switching frequency. for a cross ove r frequency of 80 khz, figure 39 shows the maximum output voltage excursion during a 1 a load transient , as the product of the output voltage an d the output capacitor is varied. choose the output capacitor based on the desired load transient response and target output voltage. 18 0 06079-070 15 70 output capacitor output voltage (c) overshoot of output voltage (%) 17 16 15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 20 25 30 35 40 45 50 55 60 65 figure 39 . percentage overshoot for a 1 a load transient response vs. output capacitor outpu t voltage for example, if the desired 1 a load transient response (overshoot) is 5% for an output voltage of 2.5 v, t h e n f r o m figure 39 output capacitor output voltage = 50 c f 20 5 . 2 c 50 = ? the adp2105/ adp210 6/ adp210 7 have been designed for operation with small ceramic output capacitors that have low esr and esl . therefore, they are comfortably able to meet tight output voltage ripple specifications. x5r or x7r dielectrics are recommended with a voltage rating of 6.3 v or 10 v. y5v and z5u di e lectrics are not recommended, due to their poor temperature and dc bias characteristics. table 10 shows a list of recommended mlcc capacitors from murata and taiyo yuden. wh e n choosing output capacitors , i t is also important to account for the loss of capacitance due to output voltage dc bias. figure 40 shows the loss of capacitance due to output voltage dc bias for three x5r mlcc capacitors from murata. 20 ?100 06079-060 voltage (v dc ) capacitance change (%) 0 ?20 ?40 ?60 ?80 0 2 4 6 1 3 2 1 4.7f 0805 x5r murata grm21br61a475k 2 10f 0805 x5r murata grm21br61a106k 3 22f 0805 x5r murata grm21br60j226m figure 40 . percentage drop - i n capacitance vs. dc b ias for ceramic capacitors (information p rovided by murata corporation) for example, to get 20 f output capacitance at an output voltage of 2.5 v, based on figure 40 , as well as to giv e some margin for temperature variance, a 22 f and a 10 f capacitor are to be
data sheet adp2105/adp2106/adp2107 rev. d | page 19 of 36 used in parallel to ensure that the output capacitance is sufficient under all conditions for stable behavior. table 10 . recommended input and out put capacitor selection for the adp2105/adp2106/adp2107 capacitor vendor murata taiyo yuden 4.7 f , 10 v x5r 0805 grm21br61a475k lmk212bj475kg 10 f , 10 v x5r 0805 grm21br61a106k lmk212bj106kg 22 f , 6.3 v x5r 0805 grm21br60j226m jmk212bj226mg inpu t capacitor selectio n the input capacitor reduces input voltage ripple caused by the switch currents on the pwin pin s . place the input capacitors as close as possible to the pwin pins. select an input capacitor capable of withstanding the rms input current for the maximum load current in your application. f or the adp2105, it is recommended that each pwin pin be bypassed with a 4.7 f or larger input capacitor. for the adp2106, bypass each pwin pin with a 10 f and a 4.7 f capacitor , and for the adp2 107, bypass each pwin pin with a 10 f capacitor. as with the output capacitor, a low esr ceramic capacitor is recommended to minimize input voltage ripple. x5r or x7r dielectrics are recommended, with a voltage rating of 6.3 v or 10 v. y5v and z5u dielectrics are not recommended due to their poor temperature and dc bias characteristics. refer to table 10 for inp ut capacitor recommendations. input filter the in pin is the power source for the adp2105/ adp210 6/ adp210 7 internal circuitry , including the voltage reference and current sense amplifier that are sensi tive to power supply noise. to prevent high frequency switching noise on the pwin pins from corruptin g the internal circuitry of the adp2105/ adp210 6/ adp210 7, a low - pass rc filter should be placed between the in pin and the pwin1 pin. the suggested input filter consists of a small 0.1 f ceramic capacitor pl aced between in and agnd and a 10 resistor placed between in and pwin1. this forms a 150 khz low - pass filter between pwin1 and in that prevents any high frequency noise on pwin1 from coupling into the in pin. soft start period to set the soft start perio d, connect a soft start capacitor (c ss ) from ss to agnd. the soft start period varies linearly with the size of the soft start capacitor, as shown in the following equation: t ss = c ss 10 9 ms for a soft start period of 1 ms, a 1 nf capacitor must be conne cted between ss and agnd. loop compensation the adp2105/ adp210 6/ adp210 7 utilize a transconductance error amplifier to compensate the external voltage loop. the open loop tr ansfer function at angular frequency (s) is given by ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = out ref out comp cs m v v sc s z g g s h ) ( ) ( where: v ref is the internal reference v oltage (0.8 v) . v out is the nominal output voltage. z comp (s) is the impedance of the compensation netw ork at the angular frequency. c out is the output c apacitor . g m is the t ran sconductance of the error amplifier (50 a/v n om inal) . g cs is the e ffective trans conductance of the current loop . g cs = 1.875 a/v for the adp2105. g cs = 2.8125 a/v for the adp2106. g cs = 3.625 a/v for the adp2107. the transconductance error amplifier drives the compensation network that consists of a r esistor ( r comp ) and capacitor ( c comp ) connected in series to form a pole and a zero, as shown in the following equation: ? ? ? ? ? ? ? ? + = ? ? ? ? ? ? ? ? + = comp comp comp comp comp comp sc c sr sc r s z 1 1 ) ( at the crossover frequency, the gain of the open loop transfer function is unity. for the compensation network impedance at the crossover frequency, t his yields the following equation : ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross cross comp v v c g g f f z ) 2 ( ) ( w here : f cross = 80 khz, the crossover frequency of the loop . c out v out is determined from the output capacitor selection section. to ensure that there is sufficient phase margin at the c rossover frequency, place the c ompensator z ero at 1/4 of the crossover frequency, as shown in the following equation: 1 4 ) 2 ( = ? ? ? ? ? ? comp comp cross c r f solving the three equations in this section simultaneously y ields the value for the compensation resistor and compensation capacitor, as shown in the following equation: ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross comp v v c g g f r ) 2 ( 8 . 0 comp cross comp r f c 2 =
adp2105/adp2106/adp2107 data sheet rev. d | page 20 of 36 bode plots 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-055 loop gain loop phase phase margin = 48 crossover frequency = 87khz adp2106 output voltage = 1.8v input voltage = 5.5v load current = 1a inductor = 2.2h (lps4012) output capacitor = 22f + 22f compensation resistor = 180k? compensation capacitor = 56pf notes 1. external components were chosen for a 5% overshoot for a 1a load transient. figure 41 . adp2106 bode plot at v in = 5.5 v, v out = 1.8 v and load = 1 a 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-056 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. adp2106 phase margin = 52 loop gain loop phase output voltage = 1.8v input voltage = 3.6v load current = 1a inductor = 2.2h (lps4012) output capacitor = 22f + 22f compensation resistor = 180k? compensation capacitor = 56pf crossover frequency = 83khz figure 42 . adp2106 bode plot at v in = 3.6 v, v out = 1.8 v , and load = 1 a 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-057 adp2105 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. loop gain loop phase phase margin = 51 crossover frequency = 71khz output voltage = 1.2v input voltage = 3.6v load current = 1a inductor = 3.3h (sd3814) output capacitor = 22f + 22f + 4.7f compensation resistor = 267k? compensation capacitor = 39pf figure 43 . adp2105 bode plot at v in = 3.6 v, v out = 1.2 v , and load = 1 a 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-058 adp2105 notes 1. external components were chosen for a 5% overshoot for a 1a load transient. crossover frequency = 79khz phase margin = 49 loop gain loop phase output voltage = 1.2v input voltage = 5.5v load current = 1a inductor = 3.3h (sd3814) output capacitor = 22f + 22f + 4.7f compensation resistor = 267k? compensation capacitor = 39pf figure 44 . adp2105 bode plot at v in = 5.5 v, v out = 1.2 v and load = 1 a 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-059 adp2107 notes 1. external components were chosen for a 10% overshoot for a 1a load transient. phase margin = 65 crossover frequency = 76khz output voltage = 2.5v input voltage = 5v load current = 1a inductor = 2h (d62lcb) output capacitor = 10f + 4.7f compensation resistor = 70k? compensation capacitor = 120pf loop phase loop gain figure 45 . adp2107 bode plot at v in = 5 v, v out = 2.5 v and load = 1 a 60 ?40 1 300 frequency (khz) loop gain (db) 10 100 50 40 30 20 10 0 ?10 ?20 ?30 loop phase (degrees) 0 45 90 135 180 06079-069 adp2107 notes 1. external components were chosen for a 10% overshoot for a 1a load transient. loop gain loop phase phase margin = 70 output voltage = 3.3v input voltage = 5v load current = 1a inductor = 2.5h (cdrh5d28) output capacitor = 10f + 4.7f compensation resistor = 70k? compensation capacitor = 120pf crossover frequency = 67khz figure 46 . adp 2107 bode plot at v in = 5 v, v out = 3.3 v , and load = 1 a
data sheet adp2105/adp2106/adp2107 rev. d | page 21 of 36 load transient respo nse 06079-087 ch2 100mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma 1 3 2 t 10.00% t lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 22f + 4.7f inductor: sd14, 2.5h compensation resistor: 270k? compensation capacitor: 39pf figure 47 . 1 a load transient response for adp2105 - 1.2 with external components chosen for 5% overshoot 06079-088 ch2 100mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma 1 3 2 t 10.00% t lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 22f inductor: sd3814, 3.3h compensation resistor: 270k? compensation capacitor: 39pf figure 48 . 1 a load transient response for adp2105 - 1.8 with external components chosen for 5% overshoot 06079-089 ch2 200mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma t 10.00% 1 3 2 t lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 4.7f inductor: cdrh5d18, 4.1h compensation resistor: 270k? compensation capacitor: 39pf figure 49 . 1 a load transient response for adp2105 - 3.3 with external components chosen for 5% overshoot 06079-090 ch2 100mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma 1 3 2 t 10.00% t lx node (switch node) output voltage (ac-coupled) output current output capacitor: 22f + 4.7f inductor: sd14, 2.5h compensation resistor: 135k? compensation capacitor: 82pf figure 50 . 1 a load transient response for adp2105 - 1.2 with external components chosen for 10% overshoot 06079-091 ch2 100mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma 1 3 2 t 10.00% t output voltage (ac-coupled) lx node (switch node) output current output capacitor: 10f + 10f inductor: sd3814, 3.3h compensation resistor: 135k? compensation capacitor: 82pf figure 51 . 1 a load transient response for adp2105 - 1.8 with external components chosen for 10% overshoot 06079-092 ch2 200mv~ ch1 2.00v ch3 1.00a ? m 20.0s a ch3 700ma 1 3 2 t 10.00% t lx node (switch node) output voltage (ac-coupled) output current output capacitor: 10f + 4.7f inductor: cdrh5d18, 4.1h compensation resistor: 135k? compensation capacitor: 82pf figure 52 . 1 a load trans ient response for adp2105 - 3.3 with external components chosen for 10% overshoot
adp2105/adp2106/adp2107 data sheet rev. d | page 22 of 36 efficiency considerations efficiency is the ratio of output power to input power. the high efficiency of the adp2105/adp2106/adp2107 has two distinct advantages . first , only a small amount of power is lost in the dc - to - dc converter package that reduces thermal constraints. second , the high efficiency delivers the maximum output power for the given input power, extending battery life in portable applications. there are f our ma jor sources of power loss in dc - to - dc converters l ike the adp2105/adp2106/adp2107 : ? power switch conduction losses ? inductor losses ? swi tching losses ? transition losses power switch conduction losses power switch conduction losses are caused by the flow of out put current through th e p - channel power switch and the n - channel synchronous rectifier, which have internal resistances ( r ds(on) ) associated with them. the amount of power loss can be approxi - mated by p sw ? cond = [ r ds(on) ? p d + r ds(on) ? n (1 ? d )] i out 2 where d = v out /v in . the internal resistance of the power switches increases with temperature but decreases with higher input voltage. figure 20 and figure 21 show the change in r ds(on) vs. input voltage, wh ereas figure 29 and figure 30 sh ow the change in r ds(on) vs. temperature for both power devices. inductor losses inductor conduction losses are caused by the flow of current through the inductor , which has an internal resistance (dcr) associated with it. larger sized inductors have smaller dcr , which can impr ove inductor conduction losses. inductor core losses are related to the magnet ic permeability of the core material. because the adp2105/adp2106/adp2107 are high switching frequency dc - to - dc converters, shielded ferrite core material is recommended for its low core losses and low emi. the total amount of inductor power loss can be ca lculated by p l = dcr i out 2 + core losses switching losses switching losses are associated with the current drawn by the driver to turn on and turn off the power devices at the switching frequency. each time a power device gate is turned on and turned of f, the driver transfers a charge q from the input supply to the gate and then from the gate to ground. the amount of power loss can by c alculated by p sw = ( c gate ? p + c gate ? n ) v in 2 f sw w here : ( c gate ? p + c gate ? n ) 600 p f. f sw = 1.2 mhz, the switching frequency. transition losses transition losses occur because the p - channel mosfet power switch cannot turn on or turn off insta ntaneously. at the middle of a n lx (switch) node transition, the power switch is providing all the inductor current, w hile the source to drain voltage of the power switch is half the input voltage , resulting in power loss. transition losses increase with load current and input voltage and occur twice for each switching cycle. the amount of power loss can be calculated by sw off on out in tran f t t i v p + = ) ( 2 where t on and t off are the rise time and fall time of the lx (switch) node , and are both ap proximately 3 ns. thermal consideratio ns in most applications, the adp2105/adp2106/adp2107 do not dissipate a lot of heat due to their high efficiency. however, in applications with high ambient temperature, low supply voltage, and high duty cycle, the heat dissipated in the package is large enough that it can cause the junction temperature of the die to exceed the maximum junction temperatur e of 125c. once the junction temperature exceeds 140c, the converter goes into thermal shutdown. to prevent any permanent damage i t recovers only after the junction temperature has decreased below 100c. therefore, thermal analysis for the chosen applica tion solution is very important to guarantee reliable performance over all conditions. the junction temperature of the die is the sum of the ambient temperature of the environment and the temperature rise of the package due to the power dissipation, as sh own in the following equation: t j = t a + t r where: t j is the junction temperature. t a is the ambient temperature. t r is the rise in temperature of the package due to the power dissipation in the package. the rise in temperature of the package is directly p roportional to the power dissipation in the package. the proportionality constant for this relationship is defined as the thermal resistance from the junction of the die to the ambient temperature, as shown in the following equation: t r = ja p d where: t r is the rise in temperature of the package. p d is the power dissipation in the package. ja is the thermal resistance from the junction of the die to the ambient temperature of the package.
data sheet adp2105/adp2106/adp2107 rev. d | page 23 of 36 for example, in an application where the adp21 07(1.8 v ) is used with an input voltage of 3.6 v, a load current of 2 a , and a maximum ambient temperature of 85 c, a t a load current of 2 a, the most significant contributor of power dissipation in the dc - to - dc converter package is the conduction loss of the power switches . using the graph of switch on resistance vs. temperature (see figure 30 ), as well as the equation of power loss given in the power switch conduction losses section, the power dissipat ion in the package can be calculated by the following: p sw ? cond = [ r ds(on) ? p d + r ds(on) ? n (1 ? d )] i out 2 = [109 m 0.5 + 90 m 0.5] (2 a) 2 400 mw the ja for the lfcsp_vq package is 40c/w, as shown in table 3 . th erefore , the rise in temperature of the package due to power dissipation is t r = ja p d = 40c/w 0.40 w = 16c the junction temperature of the converter is t j = t a + t r = 85c + 16c = 101c because the junction temperature of the converter is bel ow the maximu m junction temperature of 125c , this application operates reliably from a thermal point of view.
adp2105/adp2106/adp2107 data sheet rev. d | page 24 of 36 design example consider an application with the following specifications: input voltage = 3.6 v to 4.2 v. output voltage = 2 v. typical outpu t current = 600 ma. maximum output current = 1.2 a. soft start time = 2 ms. overshoot 100 mv under all load transient conditions. 1. choose the dc - to - dc converter that satisfies the maximum output current requirement. because the maximum output current for this application is 1.2 a, the adp2106 with a maximum output current of 1.5 a is ideal for this application. 2. see whether the output voltage desired is available as a fixed output voltage option. because 2 v is not one of the fixed output voltage options available, choose the adjustable version of adp2106. 3. the first step in external compone nt selection for an adjustable version converter is to calculate the resistance of the resistive voltage divider that sets the output voltage. k 40 a 20 v 8 . 0 = = = string fb bot i v r k 60 v 8 . 0 v 8 . 0 v 2 k 40 = ? ? ? ? ? ? ? ? ? = ? ? ? ? ? ? ? = fb fb out bot top v v v r r calculate the minimum inductor value as follows: for the adp2106: l > (0.83 h/v) v out ? l > 0.83 h/v 2 v ? l > 1.66 h next, calculate the ideal inductor value that sets the inductor peak - to - peak current ripple ( i l ) to 1/3 of the maximum load current at the maximum input voltage as follows: = ? = h ) ( 5 . 2 ) ( max load in out in out ideal i v v v v l h 2.18 h 2 . 1 2 . 4 ) 2 2 . 4 ( 2 5 . 2 = ? 4. the closest standard inductor value is 2.2 h. the maximum rms current of the inductor is to be greater than 1.2 a, and the saturation current of the inductor is to be greater than 2 a. o ne inductor that meets these criteria is the lps4012 - 2.2 h from coilcraft. 5. choose the output capacitor based on the transient response requirements. the worst - case load transient is 1.2 a, for which the overshoot must be less than 100 mv, which is 5% of t he output voltage. f or a 1 a load transient, the overshoot must be less than 4% of the output voltage , then from figure 39 : output capacitor output voltage = 60 c f 30 v 0 . 2 c 60 = ? capacitor output t aking into account the loss of capacitance due to dc bias, as shown in figure 40 , two 22 f x5r mlcc capacitors from murata (grm21br60j226m) are sufficient for this application . 6. because the adp2106 is being used in this application, the input capacito rs are 10 f and 4.7 f x5r murata capacitors (grm21br61a106k and grm21br61a475k). 7. the input filter consists of a small 0.1 f ceramic capacitor placed between in and agnd and a 10 resistor placed between in and pwin 1. 8. choose a soft start capacitor of 2 nf to achieve a soft start time of 2 ms. 9. calculate the compensation resistor and capacitor as follows: ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? = ref out out cs m cross comp v v c g g f r ) 2 ( 8 . 0 = k 215 v 8 . 0 v 2 f 30 v / a 8125 . 2 v / a 50 khz 80 ) 2 ( 8 . 0 = ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? pf 39 k 215 khz 80 2 2 = = = comp cross comp r f c
data sheet adp2105/adp2106/adp2107 rev. d | page 25 of 36 external component r ecommendations for popular output voltage options at 80 khz crossover frequency with 10% overshoot for a 1 a load transient (refer to figure 37 and figure 38). table 11. recommended external components part v out (v) c in 1 1 (f) c in 2 1 (f) c out 2 (f) l (h) r comp (k) c comp (pf) r top 3 (k) r bot 3 (k) adp2105 ( adj ) 0.9 4.7 4.7 22 + 10 2.0 135 82 5 40 adp2105 (ad j) 1.2 4.7 4.7 22 + 4.7 2.5 135 82 20 40 adp2105 (adj) 1.5 4.7 4.7 10 + 10 3.0 135 82 35 40 adp2105 (adj) 1.8 4.7 4.7 10 + 10 3.3 135 82 50 40 adp2105 (adj) 2.5 4.7 4.7 10 + 4.7 3.6 135 82 85 40 adp2105 (adj) 3.3 4.7 4 .7 10 + 4.7 4.1 135 82 125 40 adp2106 (adj) 0.9 4.7 10 22 + 10 1.5 90 100 5 40 adp2106 (adj) 1.2 4.7 10 22 + 4.7 1.8 90 100 20 40 adp2106 (adj) 1.5 4.7 10 10 + 10 2.0 90 100 35 40 adp2106 (adj) 1.8 4.7 10 10 + 10 2.2 90 100 50 40 adp2106 (adj) 2.5 4.7 10 10 + 4.7 2.5 90 100 85 40 adp2106 (adj) 3.3 4.7 10 10 + 4.7 3.0 90 100 125 40 adp2107 (adj) 0.9 10 10 22 + 10 1.2 7 0 120 5 40 adp2107 (adj) 1.2 10 10 22 + 4.7 1.5 7 0 120 20 40 adp2107 (adj) 1.5 10 10 10 + 10 1.5 70 120 35 40 adp2107 (adj) 1.8 10 10 10 + 10 1.8 7 0 120 50 40 adp2107 (adj) 2.5 10 10 10 + 4.7 1.8 7 0 120 85 40 adp2107 (adj) 3.3 10 10 10 + 4.7 2.5 7 0 120 125 40 adp2105 - 1.2 1.2 4.7 4.7 22 + 4.7 2.5 135 82 n/a n/a adp2105 - 1.5 1.5 4.7 4.7 10 + 10 3.0 135 82 n/a n/a adp2105 - 1.8 1.8 4.7 4.7 10 + 10 3.3 135 82 n/a n/a adp2105 - 3.3 3.3 4. 7 4.7 10 + 4.7 4.1 135 82 n/a n/a adp2106 - 1.2 1.2 4.7 10 22 + 4.7 1.8 90 100 n/a n/a adp2106 - 1.5 1.5 4.7 10 10 + 10 2.0 90 100 n/a n/a adp2106 - 1.8 1.8 4.7 10 10 + 10 2.2 90 100 n/a n/a adp2106 - 3.3 3.3 4.7 10 10 + 4.7 3.0 90 100 n/a n/a adp2107 - 1.2 1.2 10 10 22 + 4.7 1.5 7 0 120 n/a n/a adp2107 - 1.5 1.5 10 10 10 + 10 1.5 70 120 n/a n/a adp2107 - 1.8 1.8 10 10 10 + 10 1.8 7 0 120 n/a n/a adp2107 - 3.3 3.3 10 10 10 + 4.7 2.5 7 0 120 n/a n/a 1 4.7 f 0805 x5r 10 v murata grm21br61a475ka73l. 10 f 0805 x5r 10 v murata grm21br61a106ke19l. 2 4.7 f 0805 x5r 10 v murata grm21br61a475ka73l. 10 f 0805 x5r 10 v murata grm21br61a106ke19l. 22 f 0805 x5r 6.3 v murata grm21br60j226me39l. 3 0.5% accuracy resistor.
adp2105/adp2106/adp2107 data sheet rev. d | page 26 of 36 f or p opular o utput v oltage o ptions at 8 0 khz crossover frequency wi th 5% o vershoot for a 1 a l oad t ransient ( r efer to figure 37 and figure 38) . table 12. recommended external components part v out (v) c in 1 1 (f) c in 2 1 (f) c out 2 (f) l (h) r comp (k) c comp (pf) r top 3 (k) r bot 3 (k) adp2105( adj ) 0.9 4.7 4.7 22 + 22 + 22 2.0 270 39 5 40 adp2105 ( adj ) 1.2 4.7 4.7 22 + 22 + 4.7 2.5 270 39 20 40 adp2105 ( adj ) 1 .5 4.7 4.7 22 + 22 3.0 270 39 35 40 adp2105 ( adj ) 1.8 4.7 4.7 22 + 22 3.3 270 39 50 40 adp2105 ( adj ) 2.5 4.7 4.7 22 + 10 3.6 270 39 85 40 adp2105 ( adj ) 3.3 4.7 4 .7 22 + 4.7 4.1 270 39 125 40 adp2106 ( adj ) 0.9 4.7 10 22 + 22 + 22 1.5 180 56 5 40 adp2106 ( adj ) 1.2 4.7 10 22 + 22 + 4.7 1.8 180 56 20 40 adp2106( adj ) 1.5 4.7 10 22 + 22 2.0 180 56 35 40 adp2106 ( adj ) 1.8 4.7 10 22 + 22 2.2 180 56 50 40 adp2106 ( adj ) 2.5 4.7 10 22 + 10 2.5 180 56 85 40 adp2106 ( adj ) 3.3 4.7 10 22 + 4.7 3.0 180 56 125 40 adp2107 ( adj ) 0.9 10 10 22 + 22 + 22 1.2 140 68 5 40 adp2107 ( adj ) 1.2 10 10 22 + 22 + 4.7 1.5 140 68 20 40 adp2107 ( adj ) 1.5 10 10 22 + 22 1.5 140 68 35 40 adp2107 ( adj ) 1.8 10 10 22 + 22 1.8 140 68 50 40 adp2107 ( adj ) 2.5 10 10 22 + 10 1.8 140 68 85 40 adp2107 ( a dj ) 3.3 10 10 22 + 4.7 2.5 140 68 125 40 adp2105 - 1.2 1.2 4.7 4.7 22 + 22 + 4.7 2.5 270 39 n/a n/a adp2105 - 1.5 1.5 4.7 4.7 22 + 22 3.0 270 39 n/a n/a adp2105 - 1.8 1.8 4.7 4.7 22 + 22 3.3 270 39 n/a n/a adp2105 - 3.3 3.3 4.7 4.7 22 + 4.7 4.1 270 39 n/a n/a adp2106 - 1.2 1.2 4.7 10 22 + 22 + 4.7 1.8 180 56 n/a n/a adp2106 - 1.5 1.5 4.7 10 22 + 22 2.0 180 56 n/a n/a adp2106 - 1.8 1.8 4.7 10 22 + 22 2.2 180 56 n/a n/a adp2106 - 3.3 3.3 4.7 10 22 + 4.7 3.0 180 56 n/a n/a adp2107 - 1.2 1.2 10 10 22 + 22 + 4.7 1.5 140 68 n/a n/a adp2107 - 1.5 1.5 10 10 22 + 22 1.5 140 68 n/a n/a adp2107 - 1.8 1.8 10 10 22 + 22 1.8 140 68 n/a n/a adp2107 - 3.3 3.3 10 10 22 + 4.7 2.5 140 68 n/a n/a 1 4.7f 0805 x5r 10v murata grm21br61a475ka73l. 10f 0805 x5r 10v murata grm21br61a106ke19l. 2 4.7 f 0805 x5r 10v murata grm21br61a475ka73l. 10 f 0805 x5r 10v murata grm21br61a106ke19l. 22 f 0805 x 5r 6.3v murata grm21br60j226me39l. 3 0.5% accuracy resistor.
data sheet adp2105/adp2106/adp2107 rev. d | page 27 of 36 circuit board layout recommendations good circuit board layout is essential to obtaining t he best performance from the adp2105/ adp210 6/ adp210 7. poor circuit layout degrades the output ripple , as well as the electromagnetic interference (emi) and electromagnetic compatibility (emc) performance. figure 54 and figure 55 show the ideal circuit board layout for the adp2105/ adp210 6/ adp210 7 to achieve the highest performa nce. refer to the following guidelines if adjustments to the suggested layout are needed : ? use separate analog and power ground plane s. connect the ground reference of sensitive analog circuitry (such as compensation and output voltage divider components) to analog ground; connect the ground reference of power components (such as input and output capacitors) to power ground. in addition , connect both the ground planes to the exposed pad of the adp2105/adp2106/adp2107. ? for each pwin pin, place an input capacitor as close to the pwin pin as possible and connect the other end to the closest power ground plane. ? place the 0.1 f, 1 0 low - pass input filter between the in pin and the pwin 1 pin , as close to the in pin as possible. ? ensure that the high current loops are as short and as wide as possible. make the high current path from c in through l, c out , and the pgnd plane back t o c in as short as possible. to accomplish this, ensure that the input and output capacitors share a common pgnd plane. ? m ake the high current path from the pgnd pin through l and c out back to the pgnd plane as short as possible. to accomplish this, ensure that the pgnd pin is tied to the pgnd plane as close as possible to the input and output capacitors. ? the feedback resistor divider network is to be p lace d as close as possible to the fb pin to prevent noise pic kup . t he length of trace connecting the top o f the feedback resistor divider to the output is to be as short as possible while keeping away from the high current traces and the lx (switch ) node that can lead to noise pickup. a n analog ground plane is to be place d on either side of the fb trace to red uce noise pickup . for the low fixed voltage options (1.2 v and 1.5 v), poor routing of the out_sense trace can lead to noise pickup, adversely affecting load regulation. this can be fixed by placing a 1 nf bypass capacitor close to the fb pin. ? the placemen t and routing of the compensation components are critical for proper behavior of the adp2105/adp2106/ adp2107. the compensation components are to be placed as close to the comp pin as possib le. it is advisable to use 0402- sized compensation components for closer placement, leading to smaller parasitics. surround the compensation components with an analog ground plane to prevent noise pickup. t he metal layer under the compensation components is to be the analog ground plane .
adp2105/adp2106/adp2107 data sheet rev. d | page 28 of 36 evaluation board evaluation b oard schematic for a dp2107 ( 1.8 v) j1 u1 en vcc input voltage = 2.7v to 5.5v output voltage = 1.8v, 2a v out vin gnd out vcc out 2 1 gnd vcc adp2107-1.8 en ss lx2 agnd comp pgnd gnd gnd gnd nc paddle lx1 pwin2 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 r2 100k? c6 68pf c5 1nf r1 140k? c2 10f 1 l1 2 2h c3 22f 1 c4 22f 1 r4 0? r5 ns r3 10? c7 0.1f c1 10f 1 nc = no connect 06079-044 1 murata x5r 0805 10f: grm21br61a106ke19l 22f: grm21br60j226me39l 2 2h inductor d62lcb toko fb pwin1 in gnd figure 53 . evaluation board schematic of the adp2107 - 1.8 (bold traces a re high current paths) recommended pcb layo ut (evaluation board layout) ground ground connect the ground return of all power components such as input and output capacitors to the power ground plane. power ground plane output capacitor output capacitor c out input capacitor input capacitor output v out c in c out c in jumper to enable enable 100k pull-down v in input place the feedback resis t ors as close t o the fb pin as possible. adp2105/adp2106/adp2107 r top r bot c ss r comp c comp place the compensation components as close to the comp pin as possible. analog ground plane connect the ground return of al l sensitive analog circuit r y such as compens a tion and output vo lt age divider t o the analog ground plane. lx lx pgnd inductor (l) power ground 06079-045 figure 54 . recommended layout of top layer of adp2105/adp2106/adp2107
data sheet adp2105/adp2106/adp2107 rev. d | page 29 of 36 power ground plane input vo lt age plane connecting the two pwin pins as close as possible. connect the pgnd pin t o the power ground plane as close t o the adp2105/adp2106/adp2107 as possible. connect the exposed p ad of the adp2105/adp2106/adp2107 t o a large ground plane t o aid power dissi pa tion. feedback trace: this trace connects the t op of the resistive vo lt age divider on the fb pin t o the outpu t . place this trace as f ar awa y from the lx node and high current traces as possible t o prevent noise picku p . v in v in analog ground plane enable gnd gnd 06079-046 v out figure 55 . recommended layout of bottom layer of adp2105/adp2106/adp2107
adp2105/adp2106/adp2107 data sheet rev. d | page 30 of 36 a pplication circuits adp2107-3.3 off en ss lx2 agnd output voltage = 3.3v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 5v 10f 1 v out v out 1nf 70k 120pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.5h 2 4.7f 1 load 0a to 2a 10f 1 10f 1 10 0.1f 1 murata x5r 0805 10f: grm21br61a106ke19l 4.7f: grm21br61a475ka73l 2 sumida cdrh5d28: 2.5h notes 1. nc = no connect. 2. external components were chosen for a 10% overshoot for a 1a load transient. 06079-047 fb pwin1 in gnd figure 56 . application circuit v in = 5 v, v out = 3.3 v, l oad = 0 a to 2 a adp2107-1.5 off en ss lx2 agnd output voltage = 1.5v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 3.6v 22f 1 v out v out 1nf 140k 68pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 1.5h 2 22f 1 load 0a to 2a 10f 1 10f 1 10 0.1f 1 murata x5r 0805 10f: grm21br61a106ke19l 22f: grm21br60j226me39l 2 toko d62lcb or coilcraft lps4012 notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot for a 1a load transient. 06079-048 pwin1 in gnd fb figure 57 . application circuit v in = 3.6 v, v out = 1.5 v, l oad = 0 a to 2 a
data sheet adp2105/adp2106/adp2107 rev. d | page 31 of 36 adp2105-1.8 off en ss lx2 agnd output voltage = 1.8v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 4.2v 22f 1 v out v out 1nf 270k 39pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.7h 2 22f 1 load 0a to 1a 4.7f 1 4.7f 1 10 0.1f 1 murata x5r 0805 4.7f: grm21br61a475ka73l 22f: grm21br60j226me39l 2 toko 1098as-de2812: 2.7h notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot for a 1a load transient. 06079-049 pwin1 in gnd fb figure 58 . application circuit v in = li - ion battery, v out = 1.8 v, l oad = 0 a to 1 a adp2105-1.2 off en ss lx2 agnd output voltage = 1.2v comp on pgnd gnd gnd gnd nc lx1 pwin2 v in v in input voltage = 2.7v to 4.2v 22f 1 v out v out 1nf 135k 82pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.4h 2 4.7f 1 load 0a to 1a 4.7f 1 4.7f 1 10 0.1f 1 murata x5r 0805 4.7f: grm21br61a475ka73l 22f: grm21br60j226me39l 2 toko 1069as-db3018hct or toko 1070as-db3020hct notes 1. nc = no connect. 2. external components were chosen for a 10% overshoot for a 1a load transient. 06079-050 pwin1 in gnd fb figure 59 . application circuit v in = li - ion battery, v out = 1.2 v, l oad = 0 a to 1 a
adp2105/adp2106/adp2107 data sheet rev. d | page 32 of 36 adp2106-adj off en ss lx2 fb pwin1 agnd output voltage = 2.5v comp on pgnd in gnd gnd gnd nc gnd lx1 pwin2 v in v in input voltage = 5v fb 1nf 180k 56pf 1 2 3 4 12 11 10 9 16 15 14 13 5 6 7 8 2.5h 2 10f 1 22f 1 load 0a to 1.5a 4.7f 1 10f 1 10 0.1f 1 murata x5r 0805 4.7f: grm21br61a475ka73l 10f: grm21br61a106ke19l 22f: grm21br60j226me39l 2 coiltronics sd14: 2.5h notes 1. nc = no connect. 2. external components were chosen for a 5% overshoot for a 1a load transient. 85k 40k fb 06079-051 figure 60 . application circuit v in = 5 v, v out = 2.5 v, l oad = 0 a to 1.5 a
data sheet adp2105/adp2106/adp2107 rev. d | page 33 of 36 outline dimensions compliant to jedec standards mo-220-vggc 04-06-2012- a 1 0.65 bsc 0.25 min pin 1 indic a t or 1.95 ref 0.50 0.40 0.30 t o p view 12 max 0.80 max 0.65 ty p sea ting plane coplanarit y 0.08 1.00 0.85 0.80 0.35 0.30 0.25 0.05 max 0.02 nom 0.20 ref 2.50 2.35 sq 2.20 16 5 1 3 8 9 1 2 4 0.60 max 0.60 max pin 1 indic a t or 4.10 4.00 sq 3.90 3.75 bsc sq exposed pad for proper connection of the exposed pad, refer to the pin configuration and function descriptions section of this data sheet. bot t om view figure 61 . 16 - lead lead frame chip scale package [lfcsp_vq] 4 mm 4 mm body, very thin quad (cp - 16 - 10 ) dimensions shown in millimeters ordering guide model 1 output current temperature range output voltage package description package option adp2105acpz - 1.2 - r7 1 a ?40c to +125c 1.2 v 16 - lead lfcsp_vq cp - 16 - 10 adp2105acpz - 1.5-r7 1 a ?40c to +125c 1.5 v 16- lead lfcsp_vq cp -16-10 adp2105acpz - 1.8-r7 1 a ?40c to +125c 1.8 v 16- lead lfcsp_vq cp -16-10 adp2105acpz - 3.3-r7 1 a ?40c to +125c 3.3 v 16- lead lfcsp_vq c p -16-10 adp2105acpz -r7 1 a ?40c to +125c adj 16- lead lfcsp_vq cp -16-10 adp2106acpz - 1.2-r7 1.5 a ?40c to +125c 1.2 v 16- lead lfcsp_vq cp -16-10 adp2106acpz - 1.5-r7 1.5 a ?40c to +125c 1.5 v 16- lead lfcsp_vq cp -16-10 adp2106acpz - 1.8 - r7 1.5 a ?40c to +125c 1.8 v 16 - lead lfcsp_vq cp - 16 - 10 adp2106acpz - 3.3-r7 1.5 a ?40c to +125c 3.3 v 16- lead lfcsp_vq cp -16-10 adp2106acpz -r7 1.5 a ?40c to +125c adj 16- lead lfcsp_vq cp -16-10 adp2107acpz - 1.2-r7 2 a ?40c to +125c 1.2 v 16- lead lfcsp_vq cp -16-10 a dp2107acpz - 1.5-r7 2 a ?40c to +125c 1.5 v 16- lead lfcsp_vq cp -16-10 adp2107acpz - 1.8-r7 2 a ?40c to +125c 1.8 v 16- lead lfcsp_vq cp -16-10 adp2107acpz - 3.3-r7 2 a ?40c to +125c 3.3 v 16- lead lfcsp_vq cp -16-10 adp2107acpz -r7 2 a ?40c to +125c adj 16- lead lfcsp_vq cp -16-10 adp2105 - 1.8- eval z 1.8 v evaluation board adp2105 - eval z adjustable, but set to 2.5 v evaluation board adp2106 - 1.8 - eval z 1.8 v evaluation board adp2106 - eval z adjustable, but set to 2.5 v evaluation board adp2107 - 1.8-e val z 1.8 v evaluation board adp2107 - eval z adjustable, but set to 2.5 v evaluation board 1 z = rohs compliant part.
adp2105/adp2106/adp2107 rev. d | page 34 of 36 notes
data sheet adp2105/adp2106/adp2107 rev. d | page 35 of 36 notes
adp2105/adp2106/adp2107 rev. d | page 36 of 36 ? 2006 C 2012 analog devices, inc. all rights reserved. trademarks and registered trademarks are the property of their respective owners. d06079 - 0 - 8/12(d) notes

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